Adjustment of target signal-to-interference in outer loop power control for wireless communication systems

ABSTRACT

A method for outer loop power control which compensates for changing channel conditions. A target metric, preferably target signal-to-interference ratio (SIR), is adjusted with differing step up and step down levels to converge on a relatively low steady state level of step up and step down target metric adjustments. The initial target SIR remains fixed during an inner loop settling state, followed by incremental target SIR adjustments during a transient state, and smaller incremental target SIR adjustments in a steady state. Step sizes of the adjustments are preferably based on the target block error rate (BLER) and the number of errors detected within predetermined time intervals.

CROSS REFERENCE TO RELATED APPLICATION

This application claims priority from U.S. application Ser. No. 11/023,858 filed on Dec. 28, 2004, which claims priority from U.S. provisional application No. 60/551,872, filed Mar. 10, 2004, which is incorporated by reference as if fully set forth.

FIELD OF INVENTION

The invention generally relates to wireless communication systems. In particular, the invention relates to power control in such systems.

BACKGROUND

Wireless telecommunication systems are well known in the art. In order to provide global connectivity for wireless systems, standards have been developed and are being implemented. One current standard in widespread use is known as Global System for Mobile Telecommunications (GSM). This is considered as a so-called Second Generation mobile radio system standard (2G) and was followed by its revision (2.5G). GPRS and EDGE are examples of 2.5G technologies that offer relatively high speed data service on top of (2G) GSM networks. Each one of these standards sought to improve upon the prior standard with additional features and enhancements. In January 1998, the European Telecommunications Standard Institute—Special Mobile Group (ETSI SMG) agreed on a radio access scheme for Third Generation Radio Systems called Universal Mobile Telecommunications Systems (UMTS). To further implement the UMTS standard, the Third Generation Partnership Project (3GPP) was formed in December 1998. 3GPP continues to work on a common third generational mobile radio standard.

A typical UMTS system architecture in accordance with current 3GPP specifications is depicted in FIG. 1. The UMTS network architecture includes a Core Network (CN) interconnected with a UMTS Terrestrial Radio Access Network (UTRAN) via an interface known as Iu which is defined in detail in the current publicly available 3GPP specification documents. The UTRAN is configured to provide wireless telecommunication services to users through wireless transmit receive units (WTRUs), known as User Equipments (UEs) in 3GPP, via a radio interface known as Uu. The UTRAN has one or more Radio Network Controllers (RNCs) and base stations, known as Node Bs in 3GPP, which collectively provide for the geographic coverage for wireless communications with UEs. One or more Node Bs are connected to each RNC via an interface known as Iub in 3GPP. The UTRAN may have several groups of Node Bs connected to different RNCs; two are shown in the example depicted in FIG. 1. Where more than one RNC is provided in a UTRAN, inter-RNC communication is performed via an Iur interface.

Communications external to the network components are performed by the Node Bs on a user level via the Uu interface and the CN on a network level via various CN connections to external systems.

In general, the primary function of base stations, such as Node Bs, is to provide a radio connection between the base stations' network and the WTRUs. Typically a base station emits common channel signals allowing non-connected WTRUs to become synchronized with the base station's timing. In 3GPP, a Node B performs the physical radio connection with the UEs. The Node B receives signals over the Iub interface from the RNC that control the radio signals transmitted by the Node B over the Uu interface.

A CN is responsible for routing information to its correct destination. For example, the CN may route voice traffic from a UE that is received by the UMTS via one of the Node Bs to a public switched telephone network (PSTN) or packet data destined for the Internet. In 3GPP, the CN has six major components: 1) a serving General Packet Radio Service (GPRS) support node; 2) a gateway GPRS support node; 3) a border gateway; 4) a visitor location register; 5) a mobile services switching center; and 6) a gateway mobile services switching center. The serving GPRS support node provides access to packet switched domains, such as the Internet. The gateway GPRS support node is a gateway node for connections to other networks. All data traffic going to other operator's networks or the Internet goes through the gateway GPRS support node. The border gateway acts as a firewall to prevent attacks by intruders outside the network on subscribers within the network realm. The visitor location register is a current serving networks ‘copy’ of subscriber data needed to provide services. This information initially comes from a database which administers mobile subscribers. The mobile services switching center is in charge of ‘circuit switched’ connections from UMTS terminals to the network. The gateway mobile services switching center implements routing functions required based on current location of subscribers. The gateway mobile services switching center also receives and administers connection requests from subscribers from external networks.

The RNCs generally control internal functions of the UTRAN. The RNCs also provides intermediary services for communications having a local component via a Uu interface connection with a Node B and an external service component via a connection between the CN and an external system, for example overseas calls made from a cell phone in a domestic UMTS.

Typically a RNC oversees multiple base stations, manages radio resources within the geographic area of wireless radio service coverage serviced by the Node Bs and controls the physical radio resources for the Uu interface. In 3GPP, the Iu interface of an RNC provides two connections to the CN: one to a packet switched domain and the other to a circuit switched domain. Other important functions of the RNCs include confidentiality and integrity protection.

In many wireless communication systems, adaptive transmission power control algorithms are used. In such systems, many communications may share the same radio frequency spectrum. When receiving a specific communication, all the other communications using the same spectrum cause interference to the specific communication. As a result, increasing the transmission power level of one communication degrades the signal quality of all other communications within that spectrum. However, reducing the transmission power level too far results in undesirable received signal quality, such as measured by signal to interference ratios (SIRs) at the receivers.

Various methods of power control for wireless communication systems are well known in the art. Examples of open and closed loop power control transmitter systems for wireless communication systems are illustrated in FIGS. 2 and 3, respectively. The purpose of such systems is to rapidly vary transmitter power in the presence of a fading propagation channel and time-varying interference to minimize transmitter power while insuring that data is received at the remote end with acceptable quality.

In communication systems such as Third Generation Partnership Project (3GPP) Time Division Duplex (TDD) and Frequency Division Duplex (FDD) systems, multiple shared and dedicated channels of variable rate data are combined for transmission. Background specification data for such systems are found at 3GPP TS 25.223 v3.3.0, 3GPP TS 25.222 v3.2.0, 3GPP TS 25.224 v3.6 and Volume 3 specifications of Air-Interface for 3G Multiple System Version 1.0, Revision 1.0 by the Association of Radio Industries Businesses (ARIB). A fast method and system of power control adaptation for data rate changes resulting in more optimal performance is taught in International Publication Number WO 02/09311 A2, published 31 Jan. 2002 and corresponding U.S. patent application Ser. No. 09/904,001, filed Jul. 12, 2001 owned by the assignee of the present invention.

In 3GPP W-CDMA systems, power control is used as a link adaptation method. Dynamic power control is applied for dedicated physical channels (DPCH), such that the transmit power of the DPCHs is adjusted to achieve a quality of service (QoS) with a minimum transmit power level, thus limiting the interference level within the system.

One approach is to divide transmission power control into separate processes, referred to as outer loop power control (OLPC) and inner loop power control (ILPC). The power control system is generally referred to as either open or closed dependent upon whether the inner loop is open or closed. The outer loops of both types of systems as illustrated in the examples depicted in FIGS. 2 and 3 are closed loops. The inner loop in the open loop type of system illustrated in FIG. 2 is an open loop.

In outer loop power control, the power level of a specific transmitter is based on a target SIR value. As a receiver receives the transmissions, the quality of the received signal is measured. The transmitted information is sent in units of transport blocks (TBs), and the received signal quality can be monitored on a block error rate (BLER) basis. The BLER is estimated by the receiver, typically by a cyclic redundancy check (CRC) of the data. This estimated BLER is compared to a target quality requirement, such a target BLER, representative of QoS requirements for the various types of data services on the channel. Based on the measured received signal quality, a target SIR adjustment control signal is sent to the transmitter. The transmitter adjusts the target SIR in response to these adjustment requests.

In third generation partnership program (3GPP) wideband code division multiple access (W-CDMA) systems utilizing time division duplex (TDD) mode, the UTRAN (SRNC-RRC) sets the initial target SIR to the WTRU at the call/session establishment and then subsequently continuously adjusts the target SIR of the WTRU during the life term of the call as dictated by the observation of the uplink (UL) BLER measurement.

In inner loop power control, the receiver compares a measurement of the received signal quality, such as SIR, to a threshold value (i.e., the target SIR). If the SIR exceeds the threshold, a transmit power command (TPC) to decrease the power level is sent. If the SIR is below the threshold, a TPC to increase the power level is sent. Typically, the TPC is multiplexed with data in a dedicated channel to the transmitter. In response to received TPC, the transmitter changes its transmission power level.

Conventionally, the outer loop power control algorithm in a 3GPP system sets an initial target SIR for each coded composite transport channel (CCTrCH) based on the required target BLER, using a fixed mapping between BLER and SIR, assuming a particular “most plausible” channel condition. A CCTrCH is commonly employed for transmitting various services on a physical wireless channel by multiplexing several transport channels (TrCHs), each service on its own TrCH. In order to monitor the BLER level on a CCTrCH basis, a reference transport channel (RTrCH) may be selected among the transport channels multiplexed on the considered CCTrCH. For example, a TrCH-1 may be selected for RTrCH as it may be regarded as a mid-point of all channel conditions on the CCTrCH, including an additive white Gaussian noise (AWGN) channel. For example, FIG. 4 shows typical downlink simulation results of Wideband Code Division Multiple Access Time Division Duplex (WCDMA TDD) for various channel conditions specified in 3GPP using a zero-forcing multi-user detector. Results are shown for various propagation conditions. A static channel is represented by curve AWGN, while curves for Cases 1 through 3 represent fading channels with different multipath profiles. At a required BLER of 0.01 for the Case 1 fading channel, a predetermined transmission power can be determined from the target SIR of approximately 4.5 dB. Note that this is more than 5 dB over the target SIR for the Case 2 fading channel and more than 12 dB over the target SIR for AWGN, illustrating the large span of target SIR values depending on the assumed propagation condition.

Based on the above example, the mismatch between the required BLER and the mapped target SIR varies depending on the actual channel condition and it is large especially at very low BLERs. When the WTRU converts the target BLER to an initial target SIR, there may be an error caused by this channel condition mismatch, since the target SIR required for a target BLER varies with channel conditions. As a result, the iterative process for target SIR determination has an initial differential that must be overcome by convergence to the required target, compounded by allowing the CRC process to occur, which altogether creates an undesirable delay for target SIR convergence.

The entire power control algorithm may suffer degraded performance as a result of the delay. The delay is denoted in terms of the transmission rate unit, a transmission time interval (TTI). The smallest interval is one frame of data, typically defined as 10 ms for a 3GPP communication system. In a 3GPP system, TTIs are in lengths of 10, 20, 40, or 80 ms.

There are four main error sources in transmission power control: 1) systematic error; 2) random measurement error; 3) CCTrCH processing error; and 4) channel error. The systematic error and the random measurement error are corrected reasonably by the inner loop power control monitoring the SIR measurements. The CCTrCH processing error is corrected by either the outer loop power control or the inner loop power control by using relative SIR measurements among the codes. The channel error is related to unknown time varying channel conditions.

Accordingly, there is a need for outer loop power control that determines the actual channel conditions so that a proper value for the target SIR is used.

SUMMARY

An apparatus and method of transmission power control is provided for a wireless transmit receive unit (WTRU) that transmits data signals in a forward channel in selectively sized block allocations where the WTRU is configured to make forward channel power adjustments as a function of target metrics computed based on the data signals as received over the forward channel. A series of data signal block allocations is received spaced apart in time from the WTRU on the forward channel. Target metrics for the WTRU's forward channel power adjustments are computed based on the detection of predetermined error conditions in the signals received on the forward channel, including setting an initial target metric value and storing a last target metric computed for each block allocation of data. After a preliminary period at the initial value, the target metric is changed by a step up or a step down amount at time intervals of a predetermined length whereby the target metric is increased by the step up amount if a predetermined error condition has been detected in an immediately preceding time interval or is decreased by the step down amount if the predetermined error condition has not been detected the immediately preceding time interval. Setting the step down amount at an initial transient state level is preferably based on the required quality of signal or block error ratio (BLER), such that the initial step down amount is set at a level at least as great as a predetermined step down amount for a steady state steady state level. The step down amount has a scaling factor inversely proportional to the number of detected errors during the time interval being processed. If a predetermined error condition has been detected in an immediately preceding time interval, the step down amount is reduced by a selected amount to a lower level until the step down amount is reduced to the predetermined step down amount for the steady state steady state level.

BRIEF DESCRIPTION OF THE DRAWING(S)

FIG. 1 shows an overview of a system architecture of a conventional UMTS network.

FIG. 2 is a schematic diagram of a conventional open loop power control system for a wireless communication system which implements outer loop power control via a target SIR metric.

FIG. 3 is a schematic diagram of a conventional closed loop power control system for a wireless communication system which implements outer loop power control via a target SIR metric.

FIG. 4 is a graphical representation of required BLER versus target SIR according to a simulation of a Wideband Code Division Multiple Access Time Division Duplex (W-CDMA TDD) receiver for various channel conditions using a multi-user detector.

FIG. 5 illustrates a plot of target SIR adjustments according with a jump algorithm as applicable to downlink OLPC.

FIG. 6 illustrates a plot of target SIR adjustments of an exemplary WTRU downlink OLPC in accordance with the teachings of the present invention.

FIG. 7 illustrates a plot of target SIR adjustments of an exemplary WTRU downlink OLPC with a compressed transient state in accordance with the teachings of the present invention.

FIGS. 8A-8C illustrate a method flowchart of an exemplary downlink OLPC algorithm in accordance with the teachings of the present invention.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT(S)

The present invention is described with reference to the drawing figures wherein like numerals represent like elements throughout. The terms base station, wireless transmit/receive unit (WTRU) and mobile unit are used in their general sense. The term base station as used herein includes, but is not limited to, a base station, Node-B, site controller, access point, or other interfacing device in a wireless environment that provides WTRUs with wireless access to a network with which the base station is associated.

The term WTRU as used herein includes, but is not limited to, user equipment (UE), mobile station, fixed or mobile subscriber unit, pager, or any other type of device capable of operating in a wireless environment. WTRUs include personal communication devices, such as phones, video phones, and Internet ready phones that have network connections. In addition, WTRUs include portable personal computing devices, such as PDAs and notebook computers with wireless modems that have similar network capabilities. WTRUs that are portable or can otherwise change location are referred to as mobile units.

Although the embodiments are described in conjunction with a third generation partnership program (3GPP) wideband code division multiple access (W-CDMA) system utilizing the time division duplex mode, the embodiments are applicable to any hybrid code division multiple access (CDMA)/time division multiple access (TDMA) communication system. Additionally, the embodiments are applicable to CDMA systems, in general, such as the proposed frequency division duplex (FDD) mode of 3GPP W-CDMA.

Conventional power control methods for wireless systems such as 3GPP utilize so-called inner and outer loops. The power control system is referred to as either open or closed dependent upon whether the inner loop is open or closed. The outer loops of both types of systems are closed loops.

Pertinent portions of an open loop power control system having a “transmitting” communication station 10 and a “receiving” communication station 30 are shown in FIG. 2. Both stations 10, 30 are transceivers. Typically one is a base station, called a Node B in 3GPP, and the other a type of WTRU, called a user equipment UE in 3GPP. For clarity, only selected components are illustrated and the invention is described in terms of a preferred 3GPP system, but the invention has application to wireless communication systems in general, even such systems that perform ad hoc networking where WTRUs communicate between themselves. Power control is important to maintain quality signaling for multiple users without causing excessive interference.

The transmitting station 10 includes a transmitter 11 having a data line 12 which transports a user data signal for transmission. The user data signal is provided with a desired power level which is adjusted by applying a transmit power adjustment from an output 13 of a processor 15 to adjust the transmission power level. The user data is transmitted from an antenna system 14 of the transmitter 11.

A wireless radio signal 20 containing the transmitted data is received by the receiving station 30 via a receiving antenna system 31. The receiving antenna system will also receive interfering radio signals 21 which impact on the quality of the received data. The receiving station 30 includes an interference power measuring device 32 to which the received signal is input which device 32 outputs measured interference power data. The receiving station 30 also includes a data quality measuring device 34 into which the received signal is also input which device 34 produces a data quality signal. The data quality measuring device 34 is coupled with a processing device 36 which receives the signal quality data and computes target signal to interference ratio (SIR) data based upon a user defined quality standard parameter received through an input 37.

The receiving station 30 also includes a transmitter 38 which is coupled with the interference power measuring device 32 and the target SIR generating processor 36. The receiving station's transmitter 38 also includes inputs 40, 41, 42 for user data, a reference signal, and reference signal transmit power data, respectively. The receiving station 30 transmits its user data and the control related data and references signal via an associated antenna system 39.

The transmitting station 10 includes a receiver 16 and an associated receiving antenna system 17. The transmitting station's receiver 16 receives the radio signal transmitted from the receiving station 30 which includes the receiving station's user data 44 and the control signal and data 45 generated by the receiving station 30.

The transmitting station's transmitter's processor 15 is associated with the transmitting station's receiver 16 in order to compute a transmit power adjustment. The transmitter 11 also includes a device 18 for measuring received reference signal power which device 18 is associated with path loss computing circuitry 19.

In order to compute the transmit power adjustment, the processor 15 receives data from a target SIR data input 22 which carries the target SIR data generated by the receiver station's target SIR generating processor 36, an interference power data input 23 which carries the interference data generated by the receiving station's interference power measuring device 32, and a path loss data input 24 which carries a path loss signal that is the output of the path loss computing circuitry 19. The path loss signal is generated by the path loss computing circuitry 19 from data received via a reference signal transmit power data input 25 which carries the reference signal transmit power data originating from the receiving station 30 and a measured reference signal power input 26 which carries the output of the reference signal power measuring device 18 of the transmitter 11. The reference signal measuring device 18 is coupled with the transmitting station's receiver 16 to measure the power of the reference signal as received from the receiving station's transmitter 38. The path loss computing circuitry 19 preferably determines the path loss based upon the difference between the known reference power signal strength conveyed by input 25 and the measured received power strength conveyed by input 26.

Interference power data, reference signal power data and target SIR values are signaled to the transmitting station 10 at a rate significantly lower than the time-varying rate of the propagation channel and interference. The “inner” loop is the portion of the system which relies on the measured interface. The system is considered “open loop” because there is no feedback to the algorithm at a rate comparable to the time-varying rate of the propagation channel and interference indicating how good the estimates of minimum required transmitter power are. If required transmit power level changes rapidly, the system cannot respond accordingly to change the power adjustment in a timely manner.

With respect to the outer loop of the open loop power control system of FIG. 2, at the remote receiver station 30, the quality of the received data is evaluated via the measuring device 34. Typical metrics for digital data quality are bit error rate and block error rate. Computation of these metrics requires data accumulated over periods of time significantly longer than the period of the time-varying propagation channel and interference. For any given metric, there exists a theoretical relationship between the metric and received SIR. When enough data has been accumulated in the remote receiver to evaluate the metric, it is computed and compared with the desired metric (representing a desired quality of service) in processor 36 and an updated target SIR is then output. The updated target SIR is that value (in theory) which applied in the transmitter inner loop would cause the measured metric to converge to the desired value. Finally, the updated target SIR is passed, via the receiving station transmitter 38 and the transmitting station receiver 16, to the transmitter 11 for use in its inner loop. The update rate of target SIR is bounded by the time required to accumulate the quality statistic and practical limits on the signaling rate to the power-controlled transmitter.

With reference to FIG. 3, a communication system having a transmitting station 50 and a receiving station 70 which employs a closed loop power control system is illustrated.

The transmitting station 50 includes a transmitter 51 having a data line 52 which transports a user data signal for transmission. The user data signal is provided with a desired power level which is adjusted by applying a transmit power adjustment from an output 53 of a processor 55 to adjust the power level. The user data is transmitted via an antenna system 54 of the transmitter 51.

A wireless radio signal 60 containing the transmitted data is received by the receiving station 70 via a receiving antenna system 71. The receiving antenna system will also receive interfering radio signals 61 which impact on the quality of the received data. The receiving station 70 includes an interference power measuring device 72 to which the received signal is input which device 72 outputs measured SIR data. The receiving station 70 also includes a data quality measuring device 73 into which the received signal is also input which device 73 produces a data quality signal. The data quality measuring device 73 is coupled with a processor 74 which receives the signal quality data and computes target signal to interference ratio (SIR) data based upon a user defined quality standard parameter received through an input 75.

A combiner 76, preferably a substracter, compares the measured SIR data from the device 72 with the computed target SIR data from the processor 74, preferably by subtracting, to output an SIR error signal. The SIR error signal from the combiner 76 is input to processing circuitry 77 which generates step up/down commands based thereon.

The receiving station 70 also includes a transmitter 78 which is coupled with the processing circuitry 77. The receiving station's transmitter 78 also includes an input 80 for user data. The receiving station 70 transmits its user data and the control related data via an associate antenna system 79.

The transmitting station 50 includes a receiver 56 and an associated receiving antenna system 57. The transmitting station's receiver 56 receives the radio signal transmitted from the receiving station 70 which includes the receiving station's user data 84 and the control data 85 generated by the receiving station.

The transmitting station's transmitter's processor 55 has an input 58 associated with the transmitting station's receiver 16. The processor 55 receives the up/down command signal through input 58 and computes the transmit power adjustments based thereon.

With respect to the inner loop of the closed loop power control system, the transmitting station's transmitter 51 sets its power based upon high-rate step up and step down commands generated by the remote receiving station 70. At the remote receiving station 70, the SIR of the received data is measured by the measuring device 72 and compared with a target SIR value generated by the processor 74 via combiner 76. The target SIR is that value (in theory) which, given that the data is received with that value, results in a desired quality of service. If the measured received SIR is less than the target SIR, a step down command is issued by the processing circuitry 77, via the receiving station's transmitter 78 and the transmitting station's receiver 56, to the transmitter 51, otherwise a step up command is issued. The power control system is considered closed-loop because of the high-rate feedback of the step up and step down commands which can react in real time to the time-varying propagation channel and interference. If required transmit power level changes due to time varying interference and propagation, it quickly responds and adjusts transmit power accordingly.

With respect to the outer loop of the closed loop power control system, the quality of the received data is evaluated in the receiving station 70 by the measuring device 73. Typical metrics for digital data quality are bit error rate and block error rate. Computation of these metrics requires data accumulated over periods of time significantly longer than the period of the time-varying propagation channel and interference. For any given metric, there exists a theoretical relationship between the metric and received SIR. When enough data has been accumulated in the remote receiver to evaluate the metric, it is computed and compared with the desired metric (representing a desired quality of service) by the processor 74 and an updated target SIR is then output. The updated target SIR is that value (in theory) which applied in the receiver algorithm would cause the measured metric to converge to the desired value. The updated target SIR is then used in the inner loop to determine the direction of the step up/down commands sent to the transmitting station's power scale generating processor 55 to control the power of the transmitter 51.

For outer loop power control, irrespective of its implementation in either an open loop system as illustrated in FIG. 2 or a closed loop system as illustrated in FIG. 3, an initial target metric, such as target SIR, is set that is then recomputed based on the outer loop feedback occurring during a wireless communication. Conventionally, the adjustment the target metric is performed using a fixed step method where set increments of step up and step down are employed to converge on a desired target.

After an initial target SIR is set, the down link outer loop power control process utilizes a “jump” algorithm that adjusts a target SIR based on the result of CRC of the data. FIG. 5 graphically illustrates the use of a generic jump algorithm. Each step up and step down in target SIR is a relatively fixed step size adjustment, once at the beginning of each TTI. A CRC is preferably performed at each TTI, and step down adjustments are made for every CRC having no error, while upon a CRC error detection, a step up adjustment is made.

In a preferred embodiment of the present invention, the basic jump algorithm is represented by the following. If the CRC check of the k^(th) block does not detect an error, then target_(—) SIR(k)=target_(—) SIR(k−1)−SD (dB),  Equation 1 else, if a CRC error occurs, then target_(—) SIR(k)=target_(—) SIR(k−1)+SU (dB)  Equation 2 where step down SD and step up SU are calculated by the following equations: SD=SS*target_(—) BLER  Equation 3 SU=SS−SD  Equation 4 where SS is the step size for the adjustment to target SIR, which is further discussed below in conjunction with the preferred step size variations used in accordance to the teachings of the present invention.

There are generally three states for down link outer loop power control: a preliminary inner loop settling state, a transient state, and a steady state. An example of the adjustments to target SIR during the different down link outer loop power control states in accordance with the invention is illustrated in FIG. 6. A method and system for adjusting downlink outer loop power to control target SIR is taught in U.S. patent application Ser. No. 10/659,673, filed Sep. 10, 2003, owned by the assignee of the present invention.

As shown in FIG. 6, target SIR is preferably maintained constant throughout the inner loop settling state. In the inner loop settling state, the inner loop TPC algorithm corrects the initial system systematic error and the random measurement error without changing the initial target SIR.

In the transient state, the outer loop power control algorithm attempts to correct the initial target SIR error caused by the channel condition mismatch. Initially, the jump algorithm in the transient state preferably uses a large step down size to decrease the target SIR rapidly, i.e., it forces a CRC error to occur. In the steady state, the outer loop power control algorithm attempts to maintain a target SIR by utilizing a relatively small step down size. One aspect invention of this exemplary WTRU downlink OLPC is to transition a relatively large step size initially used in the transient state to a smaller step size utilized in the steady state. Another aspect of this example is to increase the step size in the steady state where no CRC error occurs within a predetermined period.

In the transient state, a large initial step size SS_(TS) can be calculated, for example, based upon the target BLER as follows: SS _(TS)=2 log₁₀(1/target_(—) BLER) (dB)  Equation 5 For example, where target_BLER=10 ⁻², then SS_(TS)=4 dB. Then, through the application of equations 3 and 4 above, the initial step down and step up values for the transient state SD_(T), SU_(T) are SD_(T)=(4×10⁻²)=0.04 dB and SU_(T)=(4−0.04)=3.96 dB.

The occurrence of CRC errors is used to trigger reduction in the step size until the transient state step size converges to the step size of the steady state SS_(SS). For this example, the steady state SS_(SS) is preferably calculated as follows: SS _(SS)=0.25[log₁₀(1/target_(—) BLER) (dB)  Equation 6 Preferably, when a CRC error occurs during a TTI in the transient state, the step size is preferably reduced by ½. The reduced step size is then applied to the jump algorithm. The procedure iterates until the new step size converges to the step size of the steady state. For the above example, convergence occurs after three iterations since SS_(TS)=2³*SS_(SS). Accordingly, for each TTI having a CRC error during the transient state, the next step size is preferably reduced from the initial step size SS_(TS) by ½^(n), where n is the number of TTIs since the start of transient state that contained at least one CRC error, until the new step size converges to the step size of the steady state. When convergence occurs, the steady state is entered and no further reduction of step size occurs.

FIG. 6 provides a graphic illustration of the above example in practice. At a first CRC error at point A, the target SIR is increased by approximately one half of a transient state step up according to Equation 4 (i.e., target SIR≈SU_(T)/2). The CRC error also causes an adjustment in the step down size; subsequent transport blocks received without CRC error result in a one-half decrease in target SIR according to Equation 3. When the next CRC error occurs, the step up size is reduced to one-fourth the original step up size (SU_(T)/4), target SIR is approximately increased by that amount, and the step down size is adjusted to SD_(T)/4. This algorithm continues until the adjusted step up size SU_(T) equals the steady state step up size SU_(S), which in the example shown in both FIGS. 6 and 7, is equal to SU_(T)/8. At this point, steady state is entered. The step up and step down sizes are fixed at SU_(S) and SD_(S), respectively. While the proportion value of predetermined step sizes for transient state and steady state is preferably 2³, as shown in Equations 3 and 4 and described in the above examples, this proportion value can be adjusted to suit channel conditions within the scope of the present invention.

The convergence to the steady state can be quite rapid where CRC errors are successively detected upon entering the transient state. FIG. 7 illustrates this for the above example where several transport blocks are received with CRC error immediately after the transient state is entered, resulting in successive decreases by a transient state step up SU_(T) in the target SIR. As shown in FIG. 7, the initial CRC result indicates an error at point A, which results in a step up in target SIR by approximately SU_(T)/2, and setting of the step down size to SD_(T)/2. FIG. 7 also illustrates the possibility where the first CRC result after a step up indicates an error. In such case as shown at point B, the target SIR is increased again, but by approximately one-fourth the original step size (i.e., target SIR≈SU_(T)/4). To continue this worst case scenario, a CRC error occurs again at the third TTI in the transient state. The next target SIR step up adjustment becomes approximately one-eighth the original value (i.e., target SIR≈SU_(T)/8). Because this step up is equal to the predetermined steady state step up SU_(S), the transient state ends at this point, and the steady state commences. The target SIR is consequently increased by SU_(S)=SU_(T)/8, and the step down size is set to SD_(S)=SD_(T)/8. Generally, any CRC error, regardless of when it occurs, will initiate a step up in target SIR by an amount that is half of the previous step up.

After the steady state is entered the step up and step down sizes are generally maintained at SU_(S) and SD_(S), respectively. Typically, where there is little change in the communication metrics, the steady state algorithm produces a series of successive step up and step down commands in a regular pattern (not shown) as is the case with the conventional jump algorithm. However, where the communication is subject to a rapid change in operating conditions due to changes in interference or other factors, application of the steady state algorithm can be less efficient. Accordingly, the steady state is varied from time to time to meet rapidly changing conditions.

During the steady state, when a predetermined observation period is passed with no CRC error occurrence, the step down size is preferably automatically increased. For example, as illustrated in FIGS. 6 and 7, after the passage of eight TTIs without a CRC error, the step down size is temporarily doubled so that the eighth and following consecutive step downs are twice the SD_(S) amount.

It is preferable that the observation period be relatively long as it is assumed that the target SIR is close to convergence. Preferably, the observation period is set to 5/(target BLER) consecutive TTIs. For example, if the target BLER is 0.01, then the observation period would equal 500 consecutive TTIs. The step down value 2SD_(S) remains fixed until a CRC error occurs, when it is then returned to SD_(S). This improves the convergence time when a sudden improvement in channel conditions occurs, giving rise to an excessive measured SIR compared to the desired target SIR. The steady state continues for the life of the CCTrCH communication with this type of adjustment preferably being made whenever there is no CRC error in a time increment equal to the observation period.

Alternatively, when a predetermined observation period is passed with no CRC error occurrence, the process can revert back to the transient state to reduce convergence time, and then proceed to steady state once the target SIR converges in the same manner as before. In such case, for the above example, the step down value would switch from SD_(S) to SD_(TS) as defined above and then be incrementally reduced to the steady state value is CRC errors are detected.

The outer loop algorithm described above is preferably implemented in a processor that computes the target SIR such as processor 36 of the open loop system illustrated in FIG. 2 and processor 74 of the closed loop system illustrated in FIG. 3. The implementation of the algorithm determines whether any CRC errors occur in a new TTI, adjusts the step up and step down sizes appropriately, then applies the step adjustments based on the individual CRC results.

For a 3GPP system, in both the transient and steady states, if the RTrCH is reselected (e.g., for variable bit rate services) and the target BLER of that new RTrCH is different from the old, then the SIR step sizes are recalculated based on the new target BLER. In steady state, the observation period is also updated, and the current count of blocks without error is reset to zero. In transient state, in addition to recalculating the step sizes, an additional adjustment is made to account for the convergence that may already have occurred in this state. In other words, the initial step up SU or step down SD values are not applied, but rather the current adjustment for detected CRC errors is applied. As before, the fractional step up or step down size is calculated with a factor ½^(n), where n is the number of TTIs since the start of transient state that contained at least one CRC error. For example, if the current step down size before RTrCH reselection is SD_(Told)/4, then the step down size immediately after RTrCH reselection must be set to SD_(Tnew)/4 and the step up size must be set to SU_(Tnew)/4.

In FIGS. 8A-8C, a flowchart for implementing the preferred algorithm for downlink outer loop power control in a 3GPP system is provided. In FIG. 8A, stage 300 represents preferred procedures during the inner loop settling state. In step 302, the parameters for inner loop settling time, transient state step size SS_(TS), steady state step size SS_(SS), and TTI count are initialized. The settling state starts upon activation of the downlink physical channel(s). The settling state lasts for a finite period of time, based on performance requirement. In one embodiment of the invention, inner loop settling time is set to 100 ms, for a time division duplex (TDD) communication. In another embodiment of the invention, for frequency division duplex (FDD), inner loop settling time is set to 10 or 30 ms depending on the frequency of operation of power control. During the settling state period, no adjustments are made to the initial target signal-to-interference ratio (SIR). The measured SIR converges toward the initial target SIR value as a result of inner loop power control which sends commands to the Node B requesting it to adjust its transmit power up or down based on the difference between the measured SIR(s) and the target SIR. The values for transient state step size SS_(TS) and steady state step size SS_(SS) are initialized according to Equations 5 and 6 above, respectively. The value for the TTI count is set to zero (0).

In step 304, a comparison is made between the product (TTI count * TTI length) and a predetermined inner loop settling time. If the product is greater than the inner loop settling time, then the settling state is complete, and the power control algorithm proceeds to the transient state. If not, the TTI count is incremented by one (1) in step 306, and the settling state returns to step 304 for another comparison. Thus, the algorithm stage 300 assures that enough TTIs have elapsed to allow the inner loop power control to correct initial systematic error and random measurement error.

In FIG. 8B, stage 307 represents preferred procedures for downlink outer loop power control which occur during the transient state. Step 308 is initiated by the affirmative decision of step 304 from the FIG. 8A portion of the flow chart. In step 308, the transient state parameters are initialized. The step size is preferably set to SS_(TS) according to Equation 5, the transient state step down is the step size factored by the target BLER value (i.e., SD_(T)=target_BLER*SS_(TS)), and the transient state step up SU_(T) is the difference between the step size SS_(TS) and the step down value SD_(T) (i.e., SU_(T)=SS_(TS)−SD_(T)).

In Step 310, a comparison is made between the step size SS_(TS) and the steady state step size SS_(SS). The initial value for SS_(TS) is according to Equation 5 as determined in step 302. In step 310, a decision is made as to whether step size SS_(TS) is greater than steady state step size SS_(SS). If not, the transient state is complete and the algorithm proceeds to step 321 of FIG. 8C. If so, the method proceeds to step 312 where it is checked whether N_(E) number of TTI CRC errors are at least one in number. If not, the method proceeds to step 317 where the target SIR is decreased according to the following equation: target_(—) SIR=current_target_(—) SIR−SD _(T)  Equation 7 In step 317, target SIR is set to at least a minimum value minimum_DL_SIR. That is, if target SIR is less than a predetermined value minimum_DL_SIR, the target SIR is then set equal to that minimum value. With step 317 complete, the process returns to step 310 with the newly decreased target SIR.

Returning to step 312, if at least one CRC error has been detected for the current TTI, the transient state step size SS_(TS) is set to half of the current value of SS_(TS) (step 314). Again, the step size SS_(TS) is compared to the steady state step size SS_(SS) (step 315). If the step size SS_(TS) is not greater than the steady state step size SS_(SS), then the transient state is complete and the algorithm proceeds to step 321 of FIG. 8C. Otherwise, the method proceeds to step 316, where step up SU_(T) and step down SD_(T) values are adjusted to the new step size SS_(TS) reduced in step 314, and the target SIR is increased according to the following equation: target_(—) SIR=current_target_(—) SIR+SU _(T)  Equation 8 The new target SIR value is checked for being no greater than a predetermined maximum value Maximum_DL_SIR. If the new target SIR is found to be greater than this maximum value, the new target SIR is reset to maximum value Maximum_DL_SIR. The transient state continues by returning to step 310 and repeating the cycle until the transient state step size becomes less than or equal to the steady state step size in steps 310 or 315.

Returning to step 315, if the step size SS_(TS) is greater than the steady state step size, then the target SIR is increased by the value of SU_(T) (step 316). If this adjustment to target SIR surpasses the predetermined maximum value Maximum_DL_SIR, then target SIR is set to Maximum_DL_SIR before returning to step 310 for the next TTI.

In FIG. 8C, stage 320 represents preferred procedures for the steady state portion of downlink outer loop power control. In step 321, the TTI count for the observation period is initialized to zero. At step 322, the number of CRC errors N_(E) is checked as to whether at least one error was detected in the current TTI. If at least one error is detected, then steady state parameters step down SD_(S) and step up SU_(S) are adjusted according to Equations 3 and 4 (step 325). The target SIR step size is set to the steady state step size SS_(SS) determined in step 302. The target SIR value is adjusted according to the following equation: target_(—) SIR=current_target_(—) SIR+SU _(S) −SD _(S)(N _(B) −N _(E) /N _(E))  Equation 9 where N_(B) is the number of transport blocks received on the reference TrCH in the current TTI, and N_(E) is the number of transport blocks received with a CRC error on the RTrCH in the current TTI. The purpose of scaling the step down by (N_(B)−N_(E))/N_(E) is to minimize the absolute variation in target SIR. An alternative approach would be to increase target SIR by step up SU_(S) for each block in error (i.e., by SU_(S)*N_(E)) while decreasing by step down SD_(S) for each block received without error (i.e., by SD_(S)*(N_(B)−N_(E)). However, this alternative approach results in greater overall variations in the target SIR upon detection of a CRC error, since step up SU_(S) is proportionately large compared to SD_(S).

Also at step 325, the current value of detected CRC errors N_(E) is stored as follows: Last_N_(E)=N_(E). The stored error value Last_N_(E) is useful for future TTI processing in which no CRC errors are detected, and a division-by-zero operation is averted in step 326. At step 325, the new target SIR value is checked for being no greater than value Maximum_DL_SIR. If the new target SIR is found to be greater than this maximum value, the new target SIR is reset to value Maximum_DL_SIR. The steady state continues by returning to step 322.

Returning to step 322, if there are no detected errors N_(E), then the observation period is checked (step 323) for being greater than or equal to a threshold, preferably a threshold equal to 5/(target BLER). When the observation period reaches a value greater than this threshold, step 324 commences where the step down value SD_(S) is doubled. However, the observation period will initially be less than the threshold, in which case step 324 is skipped, and the target SIR is decreased (step 326) as follows: target_(—) SIR=current target_(—) SIR−SD _(S)(N _(B)/Last_(—) N _(E))  Equation 10 If this new target SIR value is less than a minimum value Minimum_DL_SIR, the new target SIR is set to the minimum value Minimum_DL_SIR. Otherwise, it remains at the calculated value. Next, the observation period is incremented by one and the algorithm returns to step 322. The algorithm 320 then repeats until the CCTrCH becomes inactive.

Preferably, the components that implement the algorithms illustrated in FIGS. 5-8 are implemented on an single integrated circuit, such as an application specific integrated circuit (ASIC). However, portions of the algorithms may also be readily implemented on multiple separate integrated circuits.

The foregoing description makes references to outer loop power control in the context of a 3GPP system as an example only and not as a limitation. The invention is applicable to other systems of wireless communication including GSM, 2G, 2.5G or any other type of wireless communication system where the equivalent of outer loop power control is implemented. Other variations and modifications consistent with the invention will be recognized by those of ordinary skill in the art. 

1. A method of downlink outer loop transmission power control having a settling state, a transient state and a steady state, comprising: during the settling state: initializing a steady state step size parameter and a transient state step size parameter, and converging a measured signal to interference ratio (SIR) to an initial target signal to interference (SIR) using an inner loop power control; during the transient state: for each transmission time interval (TTI), setting a transient state step down parameter based on a target block error rate parameter and a transient state step size parameter, and setting a transient state step up parameter based on the transient state step down parameter and a transient state step size parameter, where the transient state step down parameter and the transient state step up parameter are used for adjusting the target SIR; adjusting the transient state step size parameter by half upon detection of an error during a TTI; and increasing the target SIR if an error is detected and decreasing the target SIR if no error is detected and the transient state step size is greater than the steady state step size; during the steady state: for each TTI, decreasing the target SIR by a steady state step down parameter if no error is detected and increasing the target SIR if an error is detected; and increasing the steady state step down parameter if no error is detected within an observation period of multiple TTIs.
 2. The method of claim 1, wherein the initial transient state step size parameter (SS_TS) is calculated relative to the target BLER as follows: SS _(—) TS=2 log 10(1/target_(—) BLER).
 3. The method of claim 1, wherein the initial steady state step size parameter (SS_SS) is calculated relative to the target BLER as follows: SS _(—) SS=0.25[log 10(1/target_(—) BLER)].
 4. The method of claim 1, wherein the initial steady state step size parameter is equal to ⅛ of the initial transient state step size parameter.
 5. The method of claim 1, wherein the steady state step down parameter is factored by the number of received transport blocks within the TTI (NB) minus the number of transport blocks with a detected error (NE) per NE.
 6. The method of claim 5, wherein during the steady state, the target SIR is adjusted as follows upon detection of an error: target SIR=current target SIR+steady state step size parameter−steady state step down parameter−the factored steady state step down parameter.
 7. The method of claim 1, further comprising leaving the transient state and entering the steady state once the transient state step size is reduced to an amount equal to or less than the initial steady state step size upon receiving enough detected errors.
 8. The method of claim 1, wherein the observation period equals the ratio of 5 divided by the target BLER value. 